High-efficiency adaptive DC/AC converter

ABSTRACT

A CCFL power converter circuit is provided using a high-efficiency zero-voltage-switching technique that eliminates switching losses associated with the power MOSFETs. An optimal sweeping-frequency technique is used in the CCFL ignition by accounting for the parasitic capacitance in the resonant tank circuit. Additionally, the circuit is self-learning and is adapted to determine the optimum operating frequency for the circuit with a given load. An over-voltage protection circuit can also be provided to ensure that the circuit components are protected in the case of open-lamp condition.

REFERENCE TO PRIOR U.S. APPLICATION

This application is a continuation of and claims priority to theco-pending patent application, Ser. No. 10/132,016, entitled“High-Efficiency Adaptive DC/AC Converter” with filing date Apr. 24,2002 and assigned to the assignee of the present invention, thedisclosure of which is hereby incorporated herein by reference.

1. FIELD OF THE INVENTION

The present invention is directed to a DC to AC power converter circuit.More particularly, the present invention provides a high efficiencycontroller circuit that regulates power delivered to a load using azero-voltage-switching technique. General utility for the presentinvention is found as a circuit for driving one or more Cold CathodeFluorescent Lamps (CCFLs), however, those skilled in the art willrecognize that the present invention can be utilized with any load wherehigh efficiency and precise power control is required.

2. DESCRIPTION OF RELATED ART

FIG. 1 depicts a convention CCFL power supply system 10. The systembroadly includes a power supply 12, a CCFL driving circuit 16, acontroller 14, a feedback loop 18, and one or more lamps CCFL associatedwith an LCD panel 20. Power supply 12 supplies a DC voltage to circuit16, and is controlled by controller 14, through transistor Q3. Circuit16 is a self-resonating circuit, known as a Royer circuit. Essentially,circuit 16 is a self-oscillating dc to ac converter, whose resonantfrequency is set by L1 and C1, and N1-N4 designate transformer windingsand number of turns of the windings. In operation, transistors Q1 and Q2alternately conduct and switch the input voltage across windings N1 andN2, respectively. If Q1 is conducting, the input voltage is placedacross winding N1. Voltages with corresponding polarity will be placedacross the other windings. The induced voltage in N4 makes the base ofQ2 positive, and Q1 conducts with very little voltage drop between thecollector and emitter. The induced voltage at N4 also holds Q2 atcutoff. Q1 conducts until the flux in the core of TX1 reachessaturation.

Upon saturation, the collector of Q1 rises rapidly (to a valuedetermined by the base circuit), and the induced voltages in thetransformer decrease rapidly. Q1 is pulled further out of saturation,and V_(CE) rises, causing the voltage across N1 to further decrease. Theloss in base drive causes Q1 to turn off, which in turn causes the fluxin the core to fall back slightly and induces a current in N4 to turn onQ2. The induced voltage in N4 keeps Q1 conducting in saturation untilthe core saturates in the opposite direction, and a similar reversedoperation takes place to complete the switching cycle.

Although the inverter circuit 16 is composed of relatively fewcomponents, its proper operation depends on complex interactions ofnonlinearities of the transistors and the transformer. In addition,variations in C1, Q1 and Q2 (typically, 35% tolerance) do not permit thecircuit 16 to be adapted for parallel transformer arrangements, sinceany duplication of the circuit 16 will produce additional, undesirableoperating frequencies, which may resonate at certain harmonics. Whenapplied to a CCFL load, this circuit produces a “beat” effect in theCCFLs, which is both noticeable and undesirable. Even if the tolerancesare closely matched, because circuit 16 operates in self-resonant mode,the beat effects cannot be removed, as any duplication of the circuitwill have its own unique operating frequency.

Some other driving systems can be found in U.S. Pat. Nos. 5,430,641;5,619,402; 5,615,093; 5,818,172. Each of these references suffers fromlow efficiency, two-stage power conversion, variable-frequencyoperation, and/or load dependence. Additionally, when the load includesCCFL(s) and assemblies, parasitic capacitances are introduced, whichaffects the impedance of the CCFL itself. In order to effectively designa circuit for proper operation, the circuit must be designed to includeconsideration of the parasitic impedances for driving the CCFL load.Such efforts are not only time-consuming and expensive, but it is alsodifficult to yield an optimal converter design when dealing with variousloads. Therefore, there is a need to overcome these drawbacks andprovide a circuit solution that features high efficiency, reliableignition of CCFLs, load-independent power regulation and singlefrequency power conversion.

SUMMARY OF THE INVENTION

Accordingly, the present invention provides an optimized system fordriving a load, obtains an optimal operation for various LCD panelloads, thereby improving the reliability of the system.

Broadly defined, the present invention provides A DC/AC convertercircuit for controllably delivering power to a load, comprising an inputvoltage source; a first plurality of overlapping switches and a secondplurality of overlapping switches being selectively coupled to saidvoltage source, the first plurality of overlapping switches defining afirst conduction path, the second plurality of overlapping switchesdefining a second conduction path. A pulse generator is provided togenerate a pulse signal. Drive circuitry receives the pulse signal andcontrols the conduction state of the first and second plurality ofswitches. A transformer is provided having a primary side and asecondary side, the primary side is selectively coupled to the voltagesource in an alternating fashion through the first conduction path and,alternately, through the second conduction path. A load is coupled tothe secondary side of the transformer. A feedback loop circuit isprovided between the load and the drive circuitry that supplies afeedback signal indicative of power being supplied to the load. Thedrive circuitry alternates the conduction state of the first and secondplurality of switches, and the overlap time of the switches in the firstplurality of switches, and the overlap time of the switches in thesecond plurality of switches, to couple the voltage source to theprimary side based at least in part on the feedback signal and the pulsesignal.

The drive circuitry is constructed to generate a first complimentarypulse signal from the pulse signal, and a ramp signal from the pulsesignal. The pulse signal is supplied to a first one of the firstplurality of switches to control the conduction state thereof, and theramp signal is compared with at least the feedback signal to generate asecond pulse signal, where a controllable conduction overlap conditionexists between the conduction state of the first and second switches ofthe first plurality of switches. The second pulse signal is supplied toa second one of the first plurality of switches and controlling theconduction state thereof. The drive circuitry further generates a secondcomplimentary pulse signal based on the second pulse signal, whereinsaid first and second complimentary pulse signals control the conductionstate of a first and second ones of the second plurality of switches,respectively. Likewise, a controllable conduction overlap conditionexists between the conduction state of the first and second switches ofthe second plurality of switches.

In method form, the present invention provides a method for controllinga zero-voltage switching circuit to deliver power to a load comprisingthe steps of supplying a DC voltage source; coupling a first and secondtransistor defining a first conduction path and a third and fourthtransistor defining a second conduction path to the voltage source and aprimary side of a transformer; generating a pulse signal to having apredetermined pulse width; coupling a load to a secondary side of saidtransformer; generating a feedback signal from the load; and controllingthe feedback signal and the pulse signal to determine the conductionstate of said first, second, third and fourth transistors.

In the first embodiment, the present invention provides a convertercircuit for delivering power to a CCFL load, which includes a voltagesource, a transformer having a primary side and a secondary side, afirst pair of switches and a second pair of switches defining a firstand second conduction path, respectively, between the voltage source andthe primary side, a CCFL load circuit coupled to the secondary side, apulse generator generating a pulse signal, a feedback circuit coupled tothe load generating a feedback signal, and drive circuitry receiving thepulse signal and the feedback signal and coupling the first pair ofswitches or the second pair of switches to the voltage source and theprimary side based on said pulse signal and said feedback signal todeliver power to the CCFL load.

Additionally, the first embodiment provides a pulse generator thatgenerates a pulse signal having a predetermined frequency. The drivecircuitry includes first, second, third and fourth drive circuits; andthe first pair of switches includes first and second transistors, andthe second pair of switches includes third and fourth transistors. Thefirst, second, third and fourth drive circuits are connected to thecontrol lines of the first, second, third and fourth transistors,respectively. The pulse signal is supplied to the first drive circuit sothat the first transistor is switched in accordance with the pulsesignal. The third drive circuit generates a first complimentary pulsesignal and a ramp signal based on the pulse signal, and supplies thefirst complimentary pulse signal to the third transistor so that thethird transistor is switched in accordance with the first complimentarypulse signal. The ramp signal and the feedback signal are compared togenerate a second pulse signal. The second pulse signal is supplied tothe second drive circuit so that the second transistor is switched inaccordance with the second pulse signal. The forth driving circuitgenerates a second complementary pulse signal based on the second pulsesignal and supplies the second complementary pulse signal to the fourthtransistor so that the fourth transistor is switched in accordance withthe second complimentary pulse signal. In the present invention, thesimultaneous conduction of the first and second transistors, and thethird and fourth transistors, respectively, controls the amount of powerdelivered to the load. The pulse signal and the second pulse signal aregenerated to overlap by a controlled amount, thus delivering power tothe load along the first conduction path. Since the first and secondcomplementary pulse signals are generated from the pulse signal andsecond pulse signal, respectively, the first and second complementarypulse signals are also generated to overlap by a controlled amount,power is delivered to the load along the second conduction path, in analternating fashion between the first and second conduction paths.

Also, the pulse signal and first complementary pulse signal aregenerated to be approximately 180° out of phase, and the second pulsesignal and the second complementary signal are generated to beapproximately 180° out of phase, so that a short circuit conditionbetween the first and second conduction paths is avoided

In addition to the converter circuit provided in the first embodiment,the second embodiment includes a flip-flop circuit coupled to the secondpulse signal, which triggers the second pulse signal to the second drivesignal only when the third transistor is switched into a conductingstate. Additionally, the second embodiment includes, a phase-lock loop(PLL) circuit having a first input signal from the primary side and asecond input signal using the feedback signal. The PLL circuit comparesthe phase difference between these two signals and supplies a controlsignal to the pulse generator to control the pulse width of the pulsesignal based on the phase difference between the first and secondinputs.

In both embodiments, the preferred circuit includes the feedback controlloop having a first comparator for comparing a reference signal with thefeedback signal and producing a first output signal. A second comparatoris provided for comparing said first output signal with the ramp signaland producing said second pulse signal based on the intersection of thefirst output signal and the ramp signal. The feedback circuit alsopreferably includes a current sense circuit receiving the feedbacksignal and generating a trigger signal, and a switch circuit between thefirst and second comparator, the switch circuit receiving the triggersignal and generating either the first output signal or a predeterminedminimum signal, based on the value of the trigger signal. The referencesignal can include, for example, a signal that is manually generated toindicate a desires power to be delivered to the load. The predeterminedminimum s voltage signal can include a programmed minimum voltagesupplied to the switches, so that an overvoltage condition does notappear across the load.

Likewise, in both embodiments described herein, an overcurrentprotection circuit can be provided that receives the feedback signal andcontrols the pulse generator based on the value of said feedback signal.An overvoltage protection can be provided to receive a voltage signalfrom across the load and the first output signal and compare the voltagesignal from across the load and the first output signal, to control thepulse generator based on the value of the voltage signal from across theload.

It will be appreciated by those skilled in the art that although thefollowing Detailed Description will proceed with reference being made topreferred embodiments and methods of use, the present invention is notintended to be limited to these preferred embodiments and methods ofuse. Rather, the present invention is of broad scope and is intended tobe limited as only set forth in the accompanying claims.

Other features and advantages of the present invention will becomeapparent as the following Detailed Description proceeds, and uponreference to the Drawings, wherein like numerals depict like parts, andwherein:

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a conventional DC/AC converter circuit;

FIG. 2 is one preferred embodiment of a DC/AC converter circuit of thepresent invention;

FIGS. 2 a-2 f is an exemplary timing diagram of the circuit of FIG. 2;

FIG. 3 is another preferred embodiment of a DC/AC converter circuit ofthe present invention;

FIGS. 3 a-3 f is an exemplary timing diagram of the circuit of FIG. 3;and

FIGS. 4 a-4 f depict emulation diagrams for the circuits shown in FIGS.2 and 3.

DETAILED DESCRIPTION OF THE INVENTION

While not wishing to be bound by example, the following DetailedDescription will proceed with reference to a CCFL panel as the load forthe circuit of the present invention. However, it will be apparent thatthe present invention is not limited only to driving one or CCFLs,rather, the present invention should be broadly construed as a powerconverter circuit and methodology independent of the particular load fora particular application.

As an overview, the present invention provides circuitry to controllablydeliver power to a load using feedback signals and pulse signals toadjust the ON time of two pairs of switches. When one pair of switchesare controllably turned ON such that their ON times overlap, power isdelivered to a load (via a transformer), along a conduction path definedby the pair of switches. Likewise, when the other pair of switches arecontrollably turned ON such that their ON times overlap, power isdelivered to a load (via a transformer), along a conduction path definedby other pair of switches. Thus, by selectively turning ON switches andcontrolling the overlap between-switches, the present invention canprecisely control power delivered to a given load. Additionally, thepresent invention includes over-current and over-voltage protectioncircuits, which discontinues power to the load in the event of a shortcircuit or open circuit condition. Moreover, the controlled switchingtopology described herein enables the circuit to operate irrespective ofthe load, and with a single operating frequency independent of theresonant effects of the transformer arrangement. These features arediscussed below with reference to the drawings.

The circuit diagram shown in FIG. 2 illustrates one preferred embodimentof a phase-shift, full-bridge, zero-voltage-switching power converter ofthe present invention. Essentially, the circuit shown in FIG. 2 includesa power source 12, a plurality of switches 80 arranged as diagonal pairsof switches defining alternating conduction paths, drive circuitry 50for driving each of the switches, a frequency sweeper 22 which generatesa square wave pulse to the drive circuitry 50, a transformer TX1 (withan associated resonant tank circuit defined by the primary side of TX1and C1) and a load. Advantageously, the present invention also includesan overlap feedback control loop 40 which controls the ON time of atleast one of each pair of switches, thereby permitting controllablepower to be delivered to the load.

A power source 12 is applied to the system. Initially, a bias/referencesignal 30 is generated for the control circuitry (in control loop 40)from the supply. Preferably, a frequency sweeper 22 generates a 50%duty-cycle pulse signal, starting with an upper frequency and sweepingdownwards at a pre-determined rate and at pre-determined steps (i.e.,square wave signal of variable pulse width). The frequency sweeper 22preferably is a programmable frequency generator, as is known in theart. The pulse signal 90 (from the sweeper 22) is delivered to B_Drive(which drives the Switch_B, i.e., controls the gate of Switch_B), and isdelivered to A_Drive, which generates a complementary pulse signal 92and a ramp signal 26. The complementary pulse signal 92 is approximately180° out of phase with pulse signal 90, and the ramp signal 26 isapproximately 90° out of phase with pulse signal, as will be describedbelow. The ramp signal is preferably a sawtooth signal, as shown in theFigure. The ramp signal 26 is compared with the output signal 24(referred to herein as CMP) of the error amplifier 32, throughcomparator 28, thus generating signal 94. The output signal 94 of thecomparator 28 is likewise a 50% duty pulse delivered to C_Drive toinitiate the turning on of Switch_C which, in turn, determines theamount of overlap between the switches B and C, and switches A and D.Its complimentary signal (phased approximately 180°) is applied toSwitch_D, via D_Drive. It will be understood by those skilled in the artthat circuits Drive_A-Drive_D are connected to the control lines (e.g.,gate) of Switch_A-Switch_D, respectively, which permits each of theswitches to controllably conduct, as described herein. By adjusting theamount of overlap between switches B, C and A, D, lamp-currentregulation is achieved. In other words, it is the amount of overlappingin the conduction state of the pairs of switches that determines theamount of power processed in the converter. Hence, switches B and C, andswitches A and D, will be referred to herein as overlapping switches.

While not wishing to be bound by example, in this embodiment, B_Drive ispreferably formed of a totem pole circuit, generic low-impedance op-ampcircuit, or emitter follower circuit. C_Drive is likewise constructed.Since both A-Drive and D_Drive are not directly connected to ground(i.e., floating), it is preferred that these drives are formed of aboot-strap circuit, or other high-side drive circuitry known in the art.Additionally, as stated above, A_Drive and D_Drive include an inverterto invert (i.e., phase) the signal flowing from B_Drive and C_Drive,respectively.

High-efficiency operation is achieved through a zero-voltage-switchingtechnique. The four MOSFETs (Switch_A-Switch_D) 80 are turned on aftertheir intrinsic diodes (D1-D4) conduct, which provides a current flowingpath of energy in the transformer/capacitor (TX1/C1) arrangement,thereby ensuring that a zero voltage is across the switches when theyare turned on. With this controlled operation, switching loss isminimized and high efficiency is maintained.

The preferred switching operation of the overlapping switches 80 isshown with reference to the timing diagrams of FIGS. 2 a-2 f. Switch_Cis turned off at certain period of the conduction of both switches B andC (FIG. 2 f). The current flowing in the tank (refer to FIG. 2) is nowflowing through diode D4 (FIG. 2 e) in Switch_D, the primary oftransformer, C1, and Switch_B, after Switch_C is turned off, therebyresonating the voltage and current in capacitor C1 and the transformeras a result of the energy delivered when switches B and C wereconducting (FIG. 2 f). Note that this condition must occur, since aninstantaneous change in current direction of the primary side of thetransformer would violate Faraday's Law. Thus, current must flow throughD4 when Switch_C turns off. Switch_D is turned on after D4 hasconducted. Similarly, Switch_B is turned off (FIG. 2 a), the currentdiverts to Diode D1 associated with Switch_A before Switch_A is turnedon (FIG. 2 e). Likewise, Switch_D is turned off (FIG. 2 d), and thecurrent is now flowing now from Switch_A, through C1, the transformerprimary and Diode D3. Switch_C is turned on after D3 has conducted (FIG.2 e). Switch_B is turned on after Switch_A is turned off which allowsthe diode D2 to conduct first before it is turned on. Note that theoverlap of turn-on time of the diagonal switches B,C and A,D determinesthe energy delivered to the transformer, as shown in FIG. 2 f.

In this embodiment, FIG. 2 b shows that the ramp signal 26 is generatedonly when Switch_A is turned on. Accordingly, Drive_A, which generatesthe ramp signal 26, preferably includes a constant current generatorcircuit (not shown) that includes a capacitor having an appropriate timeconstant to create the ramp signal. To this end, a reference current(not shown) is utilized to charge the capacitor, and the capacitor isgrounded (via, for example a transistor switch) so that the dischargerate exceeds the charge rate, thus generating the sawtooth ramp signal26. Of course, as noted above, this can be accomplished by integratingthe pulse signal 90, and thus, the ramp signal 26 can be formed using anintegrator circuit (e.g., op-amp and capacitor).

In the ignition period, a pre-determined minimum overlap between the twodiagonal switches is generated (i.e., between switches A,D and B,C).This gives a minimum energy from the input to the tank circuit includingC1, transformer, C2, C3 and the CCFL load. Note that the load can beresistive and/or capacitive. The drive frequency starts at apredetermined upper frequency until it approaches the resonant frequencyof the tank circuit and equivalent circuit reflected by the secondaryside of the transformer, a significant amount of energy is delivered tothe load where the CCFL is connected. Due to its high-impedancecharacteristics before ignition, the CCFL is subjected to high voltagefrom the energy supplied to the primary side. This voltage is sufficientto ignite the CCFL. The CCFL impedance decreases to its normal operatingvalue (e.g., about 100 Kohm to 130 Kohm), and the energy supplied to theprimary side based on the minimum-overlap operation is no longersufficient to sustain a steady state operation of the CCFL. The outputof the error amplifier 26 starts its regulating function to increase theoverlap. It is the level of the error amplifier output determines theamount of the overlap. For example:

Referring to FIGS. 2 b and 2 c and the feedback loop 40 of FIG. 2, it isimportant to note that Switch_C is turned on when the ramp signal 26(generated by Drive_A) is equal to the value of signal CMP 24 (generatedby error amplifier 32), determined in comparator 28. This is indicatedas the intersection point 36 in FIG. 2 b. To prevent a short circuit,switches A,B and C,D must never be ON simultaneously. By controlling theCMP level, the overlap time between switches A,D and B,C regulates theenergy delivered to the transformer. To adjust the energy delivered tothe transformer (and thereby adjust the energy delivered to the CCFLload), switches C and D are time-shifted with respect to switches A andB, by controlling the error amplifier output, CMP 24. As can beunderstood by the timing diagrams, if the driving pulses from the outputof comparator 28 into switches C and D are shifted to the right byincreasing the level of CMP, an increase in the overlap between switchesA,C and B,D is realized, thus increasing the energy delivered to thetransformer. In practice, this corresponds to the higher-lamp currentoperation. Conversely, shifting the driving pulses of switches C and Dto the left (by decreasing the CMP signal) decreases the energydelivered.

To this end, error amplifier 32 compares the feedback signal FB with areference voltage REF. FB is a measure of the current value through thesense resistor Rs, which is indicative of the total current through theload 20. REF is a signal indicative of the desired load conditions,e.g., the desired current to flow through the load. During normaloperation, REF=FB. If, however, load conditions are intentionallyoffset, for example, from a dimmer switch associated with an LCD paneldisplay, the value of REF will increase/decrease accordingly. Thecompared value generates CMP accordingly. The value of CMP is reflectiveof the load conditions and/or an intentional bias, and is realized asthe difference between REF and FB (i.e., REF−FB).

To protect the load and circuit from an open circuit condition at theload (e.g., open CCFL lamp condition during normal operation). the FBsignal is also preferably compared to a reference value (not shown anddifferent from the REF signal described above) at the current sensecomparator 42, the output of which defines the condition of switch 28,discussed below. This reference value can be programmable, and/oruser-definable, and preferably reflects the minimum or maximum currentpermitted by the system (for example, as may be rated for the individualcomponents, and, in particular, the CCFL load). If the value of thefeedback FB signal and the reference signal is within a permitted range(normal operation), the output of the current sense comparator is 1 (or,HIGH). This permits CMP to flow through switch 38, and the circuitoperates as described herein to deliver power to the load. If, however,the value of the FB signal and the reference signal is outside apredetermined range (open circuit or short circuit condition), theoutput of the current sense comparator is 0 (or, LOW), prohibiting theCMP signal from flowing through the switch 38. (Of course, the reversecan be true, in which the switch triggers on a LOW condition). Instead aminimal voltage Vmin is supplied by switch 38 (not shown) and applied tocomparator 28 until the current sense comparator indicates permissiblecurrent flowing through Rs. Accordingly, switch 38 includes appropriateprogrammable voltage selection Vmin for when the sense current is 0.Turning again to FIG. 2 b, the effect of this operation is a lowering ofthe CMP DC value to a nominal, or minimum, value (i.e., CMP=Vmin) sothat a high voltage condition is not appearing on the transformer TX1.Thus, the crossover point 36 is shifted to the left, thereby decreasingthe amount of overlap between complementary switches (recall Switch_C isturned ON at the intersection point 36). Likewise, current sensecomparator 42 is connected to the frequency generator 22 to turn thegenerator 22 off when the sense value is 0 (or some other preset valueindicative of an open-circuit condition). The CMP is fed into theprotection circuit 62. This is to shut off the frequency sweeper 22 ifthe CCFL is removed during operation (open-circuit condition).

To protect the circuit from an over-voltage condition, the presentembodiment preferably includes protection circuit 60, the operation ofwhich is provided below (the description of the over current protectionthrough the current sense comparator 42 is provided above). The circuit60 includes a protection comparator 62 which compares signal CMP with avoltage signal 66 derived from the load 20. Preferably, voltage signalis derived from the voltage divider C2 and C3 (i.e., in parallel withload 20), as shown in FIG. 2. In the open-lamp condition, the frequencysweeper continues sweeping until the OVP signal 66 reaches a threshold.The OVP signal 62 is taken at the output capacitor divider C2 and C3 todetect the voltage at the output of the transformer TX1. To simplify theanalysis, these capacitors also represent the lump capacitor of theequivalent load capacitance. The threshold is a reference and circuit isbeing designed so that the voltage at the secondary side of thetransformer is greater than the minimum striking voltage (e.g., as maybe required by the LCD panel) while less than the rated voltage of thetransformer. When OVP exceeds the threshold, the frequency sweeper stopsthe frequency sweeping. Meanwhile, the current-sense 42 detects nosignal across the sense resistor Rs. Therefore the signal at 24, theoutput of a switch block 38, is set to be at minimum value so thatminimum overlap between switches A,C and B,D is seen. Preferably, atimer 64 is initiated once the OVP exceeds the threshold, therebyinitiating a time-out sequence. The duration of the time-out ispreferably designed according to the requirement of the loads (e.g.,CCFLs of an LCD panel), but could alternately be set at someprogrammable value. Drive pulses are disabled once the time-out isreached, thus providing safe-operation output of the converter circuit.That is, circuit 60 provides a sufficient voltage to ignite the lamp,but will shut off after a certain period if the lamp is not connected tothe converter, so that erroneous high voltage is avoided at the output.This duration is necessary since a non-ignited lamp is similar to anopen-lamp condition.

FIGS. 3 and 3 a-3 f depict another preferred embodiment of the DC/ACcircuit of the present invention. In this embodiment, the circuitoperates in a similar manner as provided in FIG. 2 and FIGS. 2 a-2 f,however this embodiment further includes a phase lock loop circuit (PLL)70 for controlling the frequency sweeper 22, and a flip-flop circuit 72to time the input of a signal into C_Drive. As can be understood by thetiming diagrams, if the 50% driving pulses of switches C and D areshifted to the right by increasing the level of CMP, an increase in theoverlap between switches A,C and B,D is realized, thus increasing theenergy delivered to the transformer. In practice, this corresponds tothe higher-lamp current operation (as may be required, e.g., by a manualincrease in the REF voltage, described above). Conversely, shifting thedriving pulses of switches C and D to the left (by decreasing the CMPsignal) decreases the energy delivered. The phase-lock-loop circuit 70maintains the phase relationship between the feedback current (throughRs) and tank current (through TX1/C1) during normal operation, as shownin FIG. 3. The PLL circuit 70 preferably includes input signals from thetank circuit (C1 and the primary of TX1) signal 98 and Rs (FB signal,described above). Once the CCFL is ignited, and the current in the CCFLis detected through Rs, the PLL 70 circuit is activated which locks thephase between the lamp current and the current in the primary resonanttank (C1 and transformer primary). That is, the PLL is provided toadjust the frequency of the frequency sweeper 22 for any parasiticvariations such as temperature effect, mechanical arrangement likewiring between the converter and the LCD panel and distance between thelamp and metal chassis of LCD panel that affect the capacitance andinductance. Preferably, the system maintains a phase difference of 180degrees between the resonant tank circuit and the current through Rs(load current). Thus, irrespective of the particular load conditionsand/or the operating frequency of the resonant tank circuit, the systemfinds an optimal operation point.

The operation of the feedback loop of FIG. 3 is similar to thedescription above for FIG. 2. However, as shown in FIG. 3 b, thisembodiment times the output of an initiating signal through C_Drivethrough flip-flop 72. For instance, during normal operation, the outputof the error amplifier 32 is fed through the controlled switch block 38(described above), resulting in signal 24. A certain amount of overlapbetween switches A,C and B,D is seen through comparator 28 and flip-flop72 which drives switches C and D (recall D_Drive produces thecomplementary signal of C_Drive). This provides a steady-state operationfor the CCFL (panel) load. Considering the removal of the CCFL (panel)during the normal operation, CMP rises to the rail of output of theerror amplifier and triggers the protection circuit immediately. Thisfunction is inhibited during the ignition period.

Referring briefly to FIGS. 3 a-3 f, the triggering of switches C and D,through C-Drive and D_Drive, is, in this embodiment, alternating as aresult of the flip-flop circuit 72. As is shown in FIG. 3 b, theflip-flop triggers every other time, thereby initiating C_Drive (and,accordingly, D_Drive). The timing otherwise operates in the same way asdiscussed above with reference to FIGS. 2 a-2 f.

Referring now to FIGS. 4 a-4 f, the output circuit of FIG. 2 or 3 isemulated. For example, FIG. 4 a shows that at 21V input, when thefrequency sweeper approaches 75.7 KHz (0.5 us overlapping), the outputis reaching 1.67 KVp-p. This voltage is insufficient to turn on the CCFLif it requires 3300 Vp-p to ignite. As the frequency decreases to say 68KHz, the minimum overlap generates about 3.9 KVp-p at the output, whichis sufficient to ignite the CCFL. This is illustrated in FIG. 4 b. Atthis frequency, the overlap increases to 1.5 us gives output about 1.9KVp-p to operate the 130 Kohm lamp impedance. This has been shown inFIG. 4 c. As another example, FIG. 4 d illustrates the operation whilethe input voltage is 7V. At 71.4 KHz, output is 750 Vp-p before the lampis striking. As the frequency decreases, the output voltage increasesuntil the lamp ignites. FIG. 4 e shows that at 65.8 KHz, the outputreaches 3500 Vp-p. The regulation of the CCFL current is achieved byadjusting the overlap to support 130 Kohm impedance after ignition. Thevoltage across the CCFL is now 1.9 KVp-p for a 660 Vrms lamp. This isalso illustrated in FIG. 4 f. Although not shown, the emulation of thecircuit of FIG. 3 behaves in a similar manner.

It should be noted that the difference between the first and secondembodiments (i.e., by the addition of the flip flop and the PLL in FIG.3) will not effect the overall operational parameters set forth in FIGS.4 a-4 f. However, the, addition of the PLL has been determined toaccount for non-ideal impedances that develop in the circuit, and may beadded as an alternative to the circuit shown in FIG. 2. Also, theaddition of the flip-flop permits the removal of the constant currentcircuit, described above.

Thus, it is evident that there has been provided a high efficiencyadaptive DC/AC converter circuit that satisfies the aims and objectivesstated herein. It will be apparent to those skilled in the art thatmodifications are possible. For example, although the present inventionhas described the use of MOSFETs for the switched, those skilled in theart will recognize that the entire circuit can be constructed using BJTtransistors, or a mix of any type of transistors, including MOSFETs andBJTs. Other modifications are possible. For example, the drive circuitryassociated with Drive_B and Drive_D may be comprised of common-collectortype circuitry, since the associated transistors are coupled to groundand are thus not subject to floating conditions. The PLL circuitdescribed herein is preferably a generic PLL circuit 70, as is known inthe art, appropriately modified to accept the input signal and generatethe control signal, described above. The pulse generator 22 ispreferably a pulse width modulation circuit (PWM) or frequency widthmodulation circuit (FWM), both of which are well known in the art.Likewise, the protection circuit 62 and timer are constructed out ofknown circuits and are appropriately modified to operate as describedherein. Other circuitry will become readily apparent to those skilled inthe art, and all such modifications are deemed within the spirit andscope of the present invention, only as limited by the appended claims.

1. A DC to AC inverter circuit, comprising: an input DC voltage source; a plurality of switches for selectively passing said DC voltage source; a transformer having a primary side and a secondary side, said primary side being selectively coupled to said DC voltage source and receiving DC voltage from said DC voltage source in an alternating fashion through said switches; a capacitor divider electrically coupled to a cold cathode fluorescent lamp load for providing a first voltage signal representing a voltage across said cold cathode fluorescent lamp load; a timer circuit coupled to said capacitor divider for providing a time-out sequence of a predetermined duration when said first voltage signal exceeds a predetermined threshold; a protection circuit coupled to said timer circuit for shuting down said plurality of switches when said first voltage signal exceeds said predetermined threshold for said predetermined duration; and a feedback control loop circuit coupled to said plurality of switches for receiving a feedback signal indicative of power being supplied to said cold cathode fluorescent lamp load from a component receiving current from said secondary side and for controlling a conduction state of at least one of said switches so that said switches have a plurality of operating modes comprising a first mode in which said switches deliver an amount of power to said cold cathode fluorescent lamp load determined by said feedback signal, and a second mode in which said switches deliver a predetermined minimum power to said cold cathode fluorescent lamp load for a predetermined time duration.
 2. A DC to AC inverter circuit as claimed in claim 1, wherein said feedback control loop circuit comprises: an error amplifier for comparing said feedback signal to a predetermined reference signal and generating an error signal indicative of the difference between said feedback signal and said predetermined reference signal; and a flow-through switch coupled to said error amplifier and having a first conduction state wherein the output of said flow-through switch comprises a DC signal indicative of said first mode of said switches, and a second conduction state wherein the output of said flow-through switch comprises a DC signal indicative of said second mode of said switches.
 3. A DC to AC inverter controller circuit comprising: a plurality of drivers for controlling a plurality of switches in an alternating fashion allowing a transformer to receive DC voltage in an alternating fashion; a voltage input for electrically coupling to a capacitor divider and to a load and for receiving a first voltage signal representing a voltage across said load; a timer circuit coupled to said voltage input for providing a time-out sequence of a predetermined duration when said first voltage signal exceeds a predetermined threshold; a protection circuit coupled to said timer circuit for shutting down said plurality of switches when said first voltage signal exceeds said predetermined threshold for said predetermined duration; and a feedback control circuit for receiving a feedback signal indicative of power being supplied to said load from a component receiving current from a secondary side of said transformer and for controlling a conduction state of at least one of said switches to deliver power to said load not exceeding a predetermined amount during a predetermined start time duration.
 4. A liquid crystal display comprising: a plurality of switches being controlled in an alternating fashion for allowing a transformer to receive DC voltage in an alternating fashion; a capacitor divider electrically coupled to a load for providing a first voltage signal representing a voltage across said load; a timer circuit coupled to said capacitor divider for providing a time-out sequence of a predetermined duration when said first voltage signal exceeds a predetermined threshold; a protection circuit coupled to said timer circuit and said plurality of switches for shutting down said plurality of switches when said first voltage signal exceeds predetermined threshold for said predetermined duration; and a feedback control loop circuit coupled to said plurality of switches for receiving a feedback signal indicative of power being supplied to said load from a component receiving current from a secondary side of said transformer and for controlling a conduction state of at least one of said switches, said feedback control loop circuit comprises an operation state in which said switches deliver an amount of power to said load determined by said feedback signal; and an ignition state in which said switches deliver power to said load not exceeding a predetermined amount during a predetermined start time duration.
 5. A liquid crystal display as claimed in claim 4 wherein said load comprises a cold cathode fluorescent lamp.
 6. A liquid crystal display as claimed in claim 5 wherein said predetermined duration is sufficient for ignition of said cold cathode fluorescent lamp when properly operating.
 7. A liquid crystal display as claimed in claim 5 wherein said predetermined start time duration is sufficient for ignition of said cold cathode fluorescent lamp when properly operating.
 8. A liquid crystal display as claimed in claim 5 wherein said predetermined threshold represents a value of said voltage across said load greater than a minimum striking voltage of said cold cathode fluorescent lamp and less than a rated voltage of said transformer.
 9. A liquid crystal display as claimed in claim 5 wherein said transformer has a primary winding and a secondary winding.
 10. A liquid crystal display as claimed in claim 9 wherein said predetermined duration is sufficient for ignition of said cold cathode fluorescent lamp when properly operating.
 11. A liquid crystal display as claimed in claim 9 wherein said predetermined start time duration is sufficient for ignition of said cold cathode fluorescent lamp when properly operating.
 12. A liquid crystal display as claimed in claim 9 wherein said predetermined threshold represents a value of said voltage across said load greater than a minimum striking voltage of said cold cathode fluorescent lamp and less than a rated voltage of said transformer.
 13. A DC to AC inverter controller circuit as claimed in claim 3 wherein said load comprises a cold cathode fluorescent lamp.
 14. A DC to AC inverter controller circuit as claimed in claim 13 wherein said predetermined duration is sufficient for ignition of said cold cathode fluorescent lamp when properly operating.
 15. A DC to AC inverter controller circuit as claimed in claim 13 wherein said predetermined start time duration is sufficient for ignition of said cold cathode fluorescent lamp when properly operating.
 16. A DC to AC inverter controller circuit as claimed in claim 13 wherein said predetermined threshold represents a value of said voltage across said load greater than a minimum striking voltage of said cold cathode fluorescent lamp and less than a rated voltage of said transformer.
 17. A DC to AC inverter controller circuit as claimed in claim 13 wherein said transformer has a primary winding and a secondary winding.
 18. A DC to AC inverter controller circuit as claimed in claim 17 wherein said predetermined duration is sufficient for ignition of said cold cathode fluorescent lamp when properly operating.
 19. A DC to AC inverter controller circuit as claimed in claim 17 wherein said predetermined start time duration is sufficient for ignition of said cold cathode fluorescent lamp when properly operating.
 20. A DC to AC inverter controller circuit as claimed in claim 17 wherein said predetermined threshold represents a value of said voltage across said load greater than a minimum striking voltage of said cold fluorescent lamp and less than a rated voltage of said transformer. 